View AD7621_7675454.PDF datasheet online --- IC-ON-LINE

Datasheet File OCR Text:

16-bit, 1.5 lsb inl, 2 msps pulsar ? adc ad7622 rev. 0 information furnished by analog devices is believed to be accurate and reliable. however, no responsibility is assumed by analog devices for its use, nor for any infringements of patents or other rights of third parties that may result from its use. specifications subject to change without notice. no license is granted by implication or otherwise under any patent or patent rights of analog devices. trademarks and registered trademarks are the property of their respective owners. one technology way, p.o. box 9106, norwood, ma 02062-9106, u.s.a. tel: 781.329.4700 www.analog.com fax: 781.461.3113 ?2006 analog devices, inc. all rights reserved. features throughput 2 msps (wideband warp and warp mode) 1.5 msps (normal mode) inl: 0.5 lsb typical, 1.5 lsb maximum (23 ppm of fsr) 16-bit resolution with no missing codes dynamic range: 92.5 db typical sinad: 91 db minimum @ 20 khz (v ref = 2.5 v) thd: ?115 db typical @ 20 khz (v ref = 2.5 v) 2.048 v internal reference: typical drift 8 ppm/c; temp output differential input range: v ref (v ref up to 2.5 v) no pipeline delay (sar architecture) parallel (16-, or 8-bit bus) and serial 5 v/3.3 v/2.5 v interface spi?/qspi?/microwire?/dsp compatible single 2.5 v supply operation power dissipation 70 mw typical @ 2 msps with internal ref 2 w in power-down mode pb-free, 48-lead lqfp and 48-lead lfcsp_vq pin compatible with other pulsar 48-lead adcs applications medical instruments high speed data acquisition/high dynamic data acquisition digital signal processing spectrum analysis instrumentation communications ate general description the ad7622 is a 16-bit, 2 msps, charge redistribution sar, fully differential, analog-to-digital converter (adc) that operates from a single 2.5 v power supply. the part contains a high speed, 16-bit sampling adc, an internal conversion clock, an internal reference (and buffer), error correction circuits, and both serial and parallel system interface ports. it features two very high sampling rate modes (wideband warp and warp) and a fast mode (normal) for asynchronous rate applications. the ad7622 is hardware factory calibrated and tested to ensure ac parameters, such as signal-to-nois e ratio (snr), in addition to the more traditional dc parameters of gain, offset, and linearity. the ad7622 is available in pb-free only packages with operation specified from ?40c to +85c. functional block diagram 06023-001 16 control logic and calibration circuitry clock ad7622 dgnd dvdd avdd agnd ref refgnd in+ in? pd reset cnvst pdbuf refbufin pdref ref temp d[15:0] rd cs byteswap ognd ovdd busy ser/par ref amp normal serial port parallel interface switched cap dac warp ob/2c figure 1. table 1. pulsar 48-lead adc selection type/ksps 100 to 250 500 to 570 650 to 1000 >1000 pseudo differential ad7651 , ad7660 , ad7661 ad7650 , ad7652, ad7664 , ad7666 ad7653 , ad7667 true bipolar ad7610 , ad7663 ad7665 ad7612 , ad7671 true differential ad7675 ad7676 ad7677 AD7621 , ad7622, ad7623 18-bit multichannel/ ad7631 , ad7678 ad7679 ad7634 , ad7674 ad7641 , ad7643 simultaneous ad7654 ad7655 1.50 ?0.50 0 0.50 1.00 ?1.50 ?1.00 0 16384 32768 49152 65536 06023-005 inl (lsb) code positive inl = +0.43 lsb negative inl = ?0.49 lsb figure 2. integral nonlinearity vs. code
ad7622 rev. 0 | page 2 of 28 table of contents features .............................................................................................. 1 applications ....................................................................................... 1 general description ......................................................................... 1 functional block diagram .............................................................. 1 revision history ............................................................................... 2 specifications ..................................................................................... 3 timing specifications ....................................................................... 5 absolute maximum ratings ............................................................ 7 esd caution .................................................................................. 7 pin configuration and function descriptions ............................. 8 ter mi nolo g y .................................................................................... 11 typical performance characteristics ........................................... 12 applications information .............................................................. 15 circuit information .................................................................... 15 converter operation .................................................................. 15 modes of operation ................................................................... 15 transfer functions ...................................................................... 16 typical connection diagram ........................................................ 17 analog inputs .............................................................................. 17 multiplexed inputs ..................................................................... 17 driver amplifier choice ........................................................... 18 voltage reference input ............................................................ 19 power supply ............................................................................... 20 conversion control ................................................................... 20 interfaces .......................................................................................... 21 digital interface .......................................................................... 21 parallel interface ......................................................................... 21 serial interface ............................................................................ 22 master serial interface ............................................................... 22 slave serial interface .................................................................. 24 microprocessor interfacing ....................................................... 26 application hints ........................................................................... 27 layout .......................................................................................... 27 evaluating the ad7622 performance ...................................... 27 outline dimensions ....................................................................... 28 ordering guide .......................................................................... 28 revision history 6 /06revision 0: initial version
ad7622 rev. 0 | page 3 of 28 specifications avdd = dvdd = 2.5 v; ovdd = 2.3 v to 3.6 v; v ref = 2.5 v; all specifications t min to t max , unless otherwise noted. table 2. parameter conditions min typ max unit resolution 16 bits analog input voltage range v in+ ? v in? ?v ref +v ref v operating input voltage v in+ , v in? to agnd ?0.1 avdd 1 v analog input cmrr f in = 100 khz 58 db input current 2 msps throughput 3.5 a input impedance 2 throughput speed complete cycle wideband warp, warp modes 500 ns throughput rate wideband warp, warp modes 0.001 2 msps time between conversions wideband warp, warp modes 1 ms complete cycle normal mode 667 ns throughput rate normal mode 0 1.5 msps dc accuracy integral linearity error 3 t min to t max = ?40c to +85c ?1.5 0.5 +1.5 lsb 4 no missing codes 16 bits differential linearity error ?1 +1.25 lsb transition noise v ref = 2.5 v 0.5 lsb transition noise v ref = 2.048 v 0.6 lsb zero error, t min to t max 5 ?10 +10 lsb zero error temperature drift 0.5 ppm/c gain error, t min to t max 5 ?8 +8 lsb gain error temperature drift 0.5 ppm/c power supply sensitivity avdd = 2.5 v 5% 4 lsb ac accuracy dynamic range v ref = 2.5 v 91.5 92.5 db 6 signal-to-noise f in = 20 khz, v ref = 2.5 v 91 92 db f in = 20 khz, v ref = 2.048 v 89.5 90.5 db f in = 100 khz, v ref = 2.5 v 91 db spurious-free dynamic range f in = 20 khz, v ref = 2.5 v 117 db f in = 20 khz, v ref = 2.048 v 110 db f in = 100 khz, v ref = 2.5 v 101 db total harmonic distortion f in = 20 khz, v ref = 2.5 v ?115 db f in = 20 khz, v ref = 2.048 v ?109 db f in = 100 khz, v ref = 2.5 v ?100 db signal-to-(noise + distortion) f in = 20 khz, v ref = 2.5 v 91 92 db f in = 20 khz, v ref = 2.048 v 89.5 90.5 db f in = 100 khz, v ref = 2.5 v 91 db ?3 db input bandwidth 50 mhz sampling dynamics aperture delay 1 ns aperture jitter 5 ps rms transient response full-scale step 140 ns internal reference pdref = pdbuf = low output voltage ref @ 25c 2.038 2.048 2.058 v temperature drift ?40c to +85c 8 ppm/c line regulation avdd = 2.5 v 5% 15 ppm/v turn-on settling time c ref = 10 f 5 ms
ad7622 rev. 0 | page 4 of 28 parameter conditions min typ max unit refbufin output voltage refbufin @ 25c 1.19 v refbufin output resistance 6.33 k external reference pdref = pdbuf = high voltage range ref 1.8 2.5 avdd + 0.1 v current drain 2 msps throughput 150 a reference buffer pdref = high, pdbuf = low refbufin input voltage range ref = 2.048 v typ 1.05 1.2 1.30 v refbufin input current refbufin = 1.2 v 1 na temperature pin voltage output @ 25c 278 mv temperature sensitivity 1 mv/c output resistance 4.7 k digital inputs logic levels v il ?0.3 +0.6 v v ih 1.7 5.25 v i il ?1 +1 a i ih ?1 +1 a digital outputs data format 7 pipeline delay 8 v ol i sink = 500 a 0.4 v v oh i source = ?500 a ovdd ? 0.3 v power supplies specified performance avdd 2.37 2.5 2.63 v dvdd 2.37 2.5 2.63 v ovdd 2.30 9 3.6 v operating current 10 2 msps throughput avdd 11 with internal reference 24 ma avdd without internal reference 23 ma dvdd 2.5 ma ovdd 12 1 ma power dissipation 11 with internal reference 10 2 msps throughput 70 85 mw without internal reference 10 2 msps throughput 65 80 mw in power-down mode 12 pd = high 2 w temperature range 13 specified performance t min to t max ?40 +85 c 1 when using an external reference. with the internal reference, the input range is ?0.1 v to v ref . 2 see analog inputs section. 3 linearity is tested using endpoints, not best fit. 4 lsb means least significant bit. with the 2.048 v input range, 1 lsb is 62.5 v. 5 see voltage reference input section. thes e specifications do not include the error contribution from the external reference. 6 all specifications in db are referred to a full-scale input fs. tested with an input signal at 0.5 db below full-scale, unless otherwise specified. 7 parallel or serial 16-bit. 8 conversion results are available imme diately after completed conversion. 9 see the absolute maximum ratings section. 10 in wideband and warp modes. tested in parallel reading mode. 11 with internal reference, pdref and pdbuf are low; without internal re ference, pdref and pdbuf are high. 12 with all digital inputs forced to ovdd. 13 consult sales for extended temperature range.
ad7622 rev. 0 | page 5 of 28 timing specifications avdd = dvdd = 2.5 v; ovdd = 2.3 v to 3.6 v; v ref = 2.5 v; all specifications t min to t max , unless otherwise noted. table 3. parameter symbol min typ max unit conversion and reset (refer to figure 31 and figure 32 ) convert pulse width t 1 15 70 1 ns time between conversions (warp mode 2 /normal mode 3 ) t 2 500/667 ns cnvst low to busy high delay t 3 23 ns busy high all modes (except master serial read after convert) warp mode/normal mode t 4 360/485 ns aperture delay t 5 1 ns end of conversion to busy low delay t 6 10 ns conversion time (warp mode/normal mode) t 7 360/485 ns acquisition time (warp mode/normal mode) t 8 140/182 ns reset pulse width t 9 15 ns reset low to busy high delay 4 t 38 10 ns busy high time from reset low 4 t 39 500 ns parallel interface modes (refer to figure 33 to figure 36 ) cnvst low to data valid delay (warp mode/normal mode) t 10 360/485 ns data valid to busy low delay t 11 2 ns bus access request to data valid t 12 20 ns bus relinquish time t 13 2 15 ns master serial interface modes 5 (refer to figure 37 and figure 38 ) cs low to sync valid delay t 14 10 ns cs low to internal sclk valid delay 5 t 15 10 ns cs low to sdout delay t 16 10 ns cnvst low to sync delay (warp mode/normal mode) t 17 15/135 ns sync asserted to sclk first edge delay t 18 2 ns internal sclk period 6 t 19 8 20 ns internal sclk high 6 t 20 2 ns internal sclk low 6 t 21 3 ns sdout valid setup time 6 t 22 1 ns sdout valid hold time 6 t 23 0 ns sclk last edge to sync delay 6 t 24 0 ns cs high to sync hi-z t 25 10 ns cs high to internal sclk hi-z t 26 10 ns cs high to sdout hi-z t 27 10 ns busy high in master serial read after convert 6 t 28 see table 4 ns cnvst low to sync asserted delay (warp mode/normal mode) t 29 375/500 ns sync deasserted to busy low delay t 30 13 ns slave serial interface modes (refer to figure 40 and figure 41 ) external sclk setup time t 31 5 ns external sclk active edge to sdout delay t 32 1 8 ns sdin setup time t 33 5 ns sdin hold time t 34 5 ns external sclk period t 35 12.5 ns external sclk high t 36 5 ns external sclk low t 37 5 ns see notes on next page.
ad7622 rev. 0 | page 6 of 28 1 see the conversion control section. 2 all timings for wideband warp mode are the same as warp mode. 3 in warp mode only, the maximum time between conversions is 1 ms; otherwise, there is no required maximum time. 4 see the digital interface section and the reset section. 5 in serial interface modes, the sync, sclk, an d sdout timings are defined with a maximum load c l of 10 pf; otherwise, the load is 60 pf maximum. 6 in serial master read during convert mode. see table 4 for serial master read after conver t mode timing specifications. table 4. serial clock timings in master read after convert mode divsclk[1] 0 0 1 1 divsclk[0] symbol 0 1 0 1 unit sync to sclk first edge delay minimum t 18 3 3 3 3 ns internal sclk period minimum t 19 8 16 32 64 ns internal sclk period maximum t 19 20 40 60 140 ns internal sclk high minimum t 20 2 8 16 32 ns internal sclk low minimum t 21 2 8 16 32 ns sdout valid setup time minimum t 22 1 5 15 5 ns sdout valid hold time minimum t 23 0 0.5 10 28 ns sclk last edge to sync delay minimum t 24 0 0.5 9 26 ns busy high width maximum warp mode t 28 0.64 0.92 1.47 2.57 s normal mode t 28 0.76 1.04 1.59 2.69 s note in serial interface modes, the sync, sclk, and sdout timing are defined with a maximum load c l of 10pf; otherwise, the load is 60pf maximum. 500a i ol 500a i oh 1.4v to output pin c l 50pf 0 6023-002 figure . load circuit for digital interface timing, sdut, sc, and scl utputs, c l = 1 pf 0.8v 2v 2v 0.8v 0.8v 2v t delay t delay 0 6023-003 figure 4. voltage reference levels for timing
ad7622 rev. 0 | page 7 of 28 absolute maximum ratings table 5. parameter rating analog inputs/outputs in+ 1 , in?, ref, refbufin, temp, ingnd, refgnd to agnd avdd + 0.3 v to agnd ? 0.3 v ground voltage differences agnd, dgnd, ognd 0.3 v supply voltages avdd, dvdd ?0.3 v to +2.7 v ovdd ?0.3 v to +3.8 v avdd to dvdd 2.8 v avdd, dvdd to ovdd ?3.8 v to +2.8 v digital inputs ?0.3 v to +5.5 v pdref, pdbuf 2 20 ma internal power dissipation 3 700 mw internal power dissipation 4 2.5 w junction temperature 125c storage temperature range C65c to +125c 1 see analog inputs section. 2 see voltage reference input section. 3 specification is for the device in free air: 48-lead lqfp; ja = 91c/w, jc = 30c/w. 4 specification is for the device in free air: 48-lead lfcsp; ja = 26c/w. stresses above those listed under absolute maximum ratings may cause permanent damage to the device. this is a stress rating only; functional operation of the device at these or any other conditions above those indicated in the operational section of this specification is not implied. exposure to absolute maximum rating conditions for extended periods may affect device reliability. esd caution esd (electrostatic discharge) sensitive device. electros tatic charges as high as 4000 v readily accumulate on the human body and test equipment and can discharge wi thout detection. although this product features proprietary esd protection circuitry, permanent dama ge may occur on devices subjected to high energy electrostatic discharges. therefore, proper esd precautions are recommended to avoid performance degradation or loss of functionality.
ad7622 rev. 0 | page 8 of 28 pin configuration and fu nction descriptions 06023-004 36 35 34 33 32 31 30 29 28 27 26 25 13 14 15 16 17 18 19 20 21 22 23 24 1 2 3 4 5 6 7 8 9 10 11 12 48 47 46 45 44 39 38 37 43 42 41 40 pin 1 identifier top view (not to scale) agnd cnvst pd reset cs rd dgnd agnd avdd dgnd byteswap ob/2c nc = no connect ser/par d0 d1 d2/divsclk[0] busy d15 d14 d13 ad7622 d3/divsclk[1] d12 d4/ext/int d5/invsync d6/invsclk d7/rdc/sdin ognd ovdd dvdd dgnd d8/sdout d9/sclk d10/sync d11/rderror pdbuf pdref refbufin temp avdd in+ agnd agnd nc in? refgnd ref normal warp figure 5. pin configuration table 6. pin function descriptions pin no. mnemonic type 1 description 1, 36, 41, 42 agnd p analog power ground. 2, 44 avdd p input analog power pins. nominally 2.5 v. 3 dgnd p digital power ground. 4 byteswap di parallel mode selection (8-bit/16-bit). when high, the lsb is output on d[15:8] and the msb is output on d[7:0]; when low, the lsb is output on d[7:0] and the msb is output on d[15:8]. 5 ob/ 2c di straight binary/binary twos complement output. wh en high, the digital output is straight binary; when low, the msb is inverted resulting in a twos complement output from its internal shift register. 6 warp di conversion mode selection. when warp = high and normal = high, this selects wideband warp mode with slightly improved linearity and thd. when warp = high and normal = low, this selects warp mode. in either mode, these are the fastes t modes; maximum throughput is achievable, and a minimum conversion rate must be applie d to guarantee full specified accuracy. 7 normal di conversion mode selection. when normal = low and warp = low, this input selects normal mode where full accuracy is maintained independent of the minimum conversion rate. 8 ser/ par di/o serial/parallel selection input. when ser/ par = high, the serial interface is selected and some bits of the data bus are used as a serial port; the remaining data bits are high impedance outputs. when ser/ par = low, the parallel port is selected. 9, 10 d[0:1] do bit 0 and bit 1 of the parallel port data output bu s. these pins are always outputs, regardless of the interface mode. 11, 12 d[2:3] di/o when ser/ par = low, these outputs are used as bit 2 an d bit 3 of the parallel port data output bus. or divsclk[0:1] when ser/ par = high, serial clock division selection. when using serial master read after convert mode (ext/ int = low, rdc/sdin = low), these inputs can be used to slow down the internally generated serial clock that clocks the data output. in other serial modes, thes e pins are high impedance outputs. 13 d4 di/o when ser/ par = low, this output is used as bit 4 of the parallel port data output bus. or ext/ int when ser/ par = high, serial clock source select. this input is used to select the internally generated (master) or external (slave) serial data clock. when ext/ int = low, master mode. the internal serial clock is selected on sclk output. when ext/ int = high, slave mode. the output data is sync hronized to an external clock signal, gated by cs , connected to the sclk input.
ad7622 rev. 0 | page 9 of 28 pin no. mnemonic type 1 description 14 d5 di/o when ser/ par = low, this output is used as bit 5 of the parallel port data output bus. or invsync when ser/ par = high, invert sync select. in serial master mode (ext/ int = low), this input is used to select the active state of the sync signal. when invsync = low, sync is active high. when invsync = high, sync is active low. 15 d6 di/o when ser/ par = low, this output is used as bit 6 of the parallel port data output bus. or invsclk when ser/ par ] = high, invert sclk select. in all se rial modes, this in put is used to invert the sclk signal. 16 d7 di/o when ser/ par = low, this output is used as bit 7 of the parallel port data output bus. or rdc when ser/ par = high, read during convert. when using serial master mode (ext/ int = low), rdc is used to select the read mode. when rdc = high, the previous conversion result is output on sdout during conversion and the period of sclk changes (see the master serial interface section). when rdc = low (read after convert), the current result can be output on sdout only when the conversion is complete. or sdin when ser/ par = low, serial data in. when using serial slave mode, (ext/ int = high), sdin could be used as a data input to daisy-chain the conversion results from two or more adcs onto a single sdout line. the digital data level on sdin is output on sdout with a delay of 16 sclk periods after the initiation of the read sequence. if not used, connect to ovdd or ognd. 17 ognd p input/output interface digital power ground. 18 ovdd p input/output interface digital power. nominally at the same supply as the supply of the host interface (2.5 v or 3 v). 19 dvdd p digital power. nominally at 2.5 v. 20 dgnd p digital power ground. 21 d8 do when ser/ par = low, this output is used as bit 8 of the parallel port data output bus. or sdout when ser/ par = high, serial data output. in serial mode, this pin is us ed as the serial data output synchronized to sclk. conversion results are stored in an on-chip register. the ad7622 provides the conversion result, msb first, from its internal shift re gister. the data format is determined by the logic level of ob/ 2c . in master mode, ext/ int = low, sdout is valid on both edges of sclk. in slave mode, ext/ int = high: when invsclk = low, sdout is updated on sclk ri sing edge and valid on the next falling edge. 2 when invsclk = high, sdout is updated on sclk fa lling edge and valid on the next rising edge. 2 22 d9 di/o when ser/ par = low, this output is used as bit 9 of the parallel port data output bus. or sclk when ser/ par = high, serial clock. in all serial modes, this pin is used as the serial data clock input or output, dependin g upon the logic state of the ext/ int pin. the active edge where the data sdout is updated, depends on the logic state of the invsclk pin. 23 d10 do when ser/ par = low, this output is used as bit 10 of the parallel port data output bus. or sync when ser/ par = high, frame synchronization. in serial master mode (ext/ int = low), this output is used as a digital output frame synchronization for use with the internal data clock. when a read sequence is initiated and invsync = low, sync is driven high and remains high while sdout output is valid. when a read sequence is initiated and invsync = high, sync is driven low and remains low while sdout output is valid. 24 d11 do when ser/ par = low, this output is used as bit 11 of the parallel port data output bus. or rderror when ser/ par = high, read error. in serial slave mode (ext/ int = high), this output is used as an incomplete read error flag. if a data read is started and not completed when the current conversion is complete, the current data is lost and rderror is pulsed high. 25 to 28 d[12:15] do bit 12 to bit 15 of the parallel port data output bu s. these pins are always outputs, regardless of the interface mode. 29 busy do busy output. transitions high when a conversion is started and remains high until the conversion is complete and the data is latched into the on-chi p shift register. the falling edge of busy can be used as a data-ready clock signal. 30 dgnd p digital power ground.
ad7622 rev. 0 | page 10 of 28 pin no. mnemonic type 1 description 31 rd di read data. when cs and rd are both low, the interface parallel or serial output bus is enabled. 32 cs di chip select. when cs and rd are both low, the interface parallel or serial output bus is enabled. cs is also used to gate the exte rnal clock in slave serial mode. 33 reset di reset input. when high, resets the ad7622. current conversion, if any, is aborted. falling edge of reset enables the calibration mode indicated by pulsing busy high. refer to the reset section. if not used, this pin can be tied to dgnd. 34 pd di power-down input. when high, power downs the adc. power consumption is reduced and conversions are inhibited after the current one is completed. 35 cnvst di conversion start. a falling edge on cnvst puts the internal sample-and-hold into the hold state and initiates a conversion. 37 ref ai/o reference output/input. when pdref/pdbuf = low, the internal reference and buffer are enabled producing 2.048 v on this pin. when pdref/pdbuf = high, the internal reference and buffer are disabled allowing an externally supplied voltage reference up to avdd volts. decoupling is required with or without the internal reference and buffer. refer to the voltage reference input section. 38 refgnd ai reference input analog ground. 39 in? ai differential negative analog input. 40 nc no connect. 43 in+ ai differential positive analog input. 45 temp ao temperature sensor analog output. normally, 278 mv @ 25c with a temperature coefficient of 1 mv/c. this pin can be used to measure the temperature of the ad7622. see the temperature sensor section. 46 refbufin ai/o internal reference output/reference buffer input. when pdref/pdbuf = low, the internal reference an d buffer are enabled producing the 1.2 v (typical) band gap output on this pin, which needs external decoupling. the internal fixed gain reference buffer uses this to produce 2.048 v on the ref pin. when using an external reference with the internal reference buffer (pdbuf = low, pdref = high), applying 1.2 v on this pin produces 2.048 v on the ref pin. refer to the voltage reference input section. 47 pdref di internal reference power-down input. when low, the internal reference is enabled. when high, the internal reference is powered down and an external reference must been used. 48 pdbuf di internal reference buffer power-down input. when low, the buffer is enabled (must be low when using internal reference). when high, the buffer is powered-down. 1 ai = analog input; ai/o = bidirectional analog; ao = analog output; di = digital input; di/o = bidirectional digital; do = dig ital output; p = power. 2 with an sclk period (2 t 32 ). with an sclk period < (2 t 32 ), sdout is valid on the next rising edge with invsclk = low and next falling edge with invsclk = high.
ad7622 rev. 0 | page 11 of 28 terminology integral nonlinearity error (inl) linearity error refers to the deviation of each individual code from a line drawn from negative full scale through positive full scale. the point used as negative full scale occurs ? lsb before the first code transition. positive full scale is defined as a level 1? lsb beyond the last code transition. the deviation is measured from the middle of each code to the true straight line. differential nonlinearity error (dnl) in an ideal adc, code transitions are 1 lsb apart. differential nonlinearity is the maximum deviation from this ideal value. it is often specified in terms of resolution for which no missing codes are guaranteed. gain error the first transition (from 00000 to 00001) should occur for an analog voltage ? lsb above the nominal negative full scale (?2.0479688 v for the 2.048 v range). the last transition (from 11110 to 11111) should occur for an analog voltage 1? lsb below the nominal full scale (+2.0479531 v for the 2.048 v range). the gain error is the deviation of the difference between the actual level of the last transition and the actual level of the first transition from the difference between the ideal levels. zero error the zero error is the difference between the ideal midscale input voltage (0 v) and the actual voltage producing the midscale output code. dynamic range it is the ratio of the rms value of the full scale to the rms noise measured with the inputs shorted together. the value for dynamic range is expressed in decibels. signal-to-noise ratio (snr) snr is the ratio of the rms value of the actual input signal to the rms sum of all other spectral components below the nyquist frequency, excluding harmonics and dc. the value for snr is expressed in decibels. total harmonic distortion (thd) thd is the ratio of the rms sum of the first five harmonic components to the rms value of a full-scale input signal and is expressed in decibels. signal to (noise + distortion) ratio (sinad) sinad is the ratio of the rms value of the actual input signal to the rms sum of all other spectral components below the nyquist frequency, including harmonics but excluding dc. the value for sinad is expressed in decibels. spurious-free dynamic range (sfdr) the difference, in decibels (db), between the rms amplitude of the input signal and the peak spurious signal. effective number of bits (enob) enob is a measurement of the resolution with a sine wave input. it is related to sinad and is expressed in bits by enob = [( sinad db ? 1.76)/6.02] aperture delay aperture delay is a measure of the acquisition performance and is measured from the falling edge of the cnvst input to when the input signal is held for a conversion. transient resp onse the time required for the ad7622 to achieve its rated accuracy after a full-scale step function is applied to its input. reference voltage temperature coefficient it is derived from the typical shift of output voltage at 25c on a sample of parts maximum and minimum reference output voltage (v ) measured at t , t(25c), and t . it is expressed in ppm/c using ref min max () () ( ) () () 6 10 c25 cppm/ ? ? = min max ref ref ref ref tt v minvmaxv tcv where: v ref ( max ) = maximum v ref at t min , t(25c), or t max v ref ( min ) = minimum v ref at t min , t(25c), or t max v ref (25 c ) = v ref at 25c t max = +85c t min = C40c
ad7622 rev. 0 | page 12 of 28 typical performance characteristics 1.50 ?0.50 0 0.50 1.00 ?1.50 ?1.00 0 16384 32768 49152 65536 06023-005 inl (lsb) code positive inl = +0.43 lsb negative inl = ?0.49 lsb figure 6. integral nonlinearity vs. code 00 44 76 00 50000 0 100000 150000 200000 250000 7ff8 7ff9 7ffa 7ffb 7ffc 7ffd 7ffe 7fff 8000 27695 196433 06023-006 counts codes in hex = 0.5 v ref = 2.5v 36872 figure 7. histogram of 261,120 conversions of a dc input at the code center (external reference) 06023-007 v ref (v) temperature (c) 2.0470 2.0472 2.0474 2.0476 2.0478 2.0480 2.0482 2.0484 2.0486 ?55 ?35 ?15 5 25 45 65 85 105 125 figure 8. typical reference voltage output vs. temperature (2 units) 1.25 ?1.00 ?0.75 ?0.50 ?0.25 0 0.25 0.50 0.75 1.00 0 16384 32768 49152 65536 06023-008 dnl (lsb) code figure 9. differential nonlinearity vs. code 00 784 37789 457 10 0 40000 80000 120000 160000 200000 7ff8 7ff9 7ffa 7ffb 7ffc 7ffd 7ffe 7fff 8000 50640 171449 06023-009 counts codes in hex = 0.5 v ref = 2.048v figure 10. histogram of 261,120 conversions of a dc input at the code center (internal reference) 06023-010 zero error, gain error (lsb) temperature (c) ?4 ?3 ?2 ?1 0 1 2 3 4 ?55 ?35 ?15 5 25 45 65 85 105 125 zero error gain error figure 11. zero error, gain error vs. temperature
ad7622 rev. 0 | page 13 of 28 0 ?140 ?120 ?100 ?80 ?60 ?40 ?20 ?160 ?180 0 100 200 300 400 500 600 700 800 900 1000 06023-011 amplitude (db of full scale) frequency (khz) f s = 2msps f in = 20.1khz snr = 92db thd = ?117db sfdr = 103db sinad = 92db figure 12. fft 20 khz 95 79 81 83 85 87 89 91 93 77 75 16.0 12.8 13.2 13.6 14.0 14.4 14.8 15.2 15.6 12.4 12.0 1 10 100 1000 06023-012 snr, sinad (db) enob (bits) frequency (khz) snr enob sinad figure 13. snr, sinad, and enob vs. frequency ? 70 ?80 ?90 ?100 ?110 ?120 ?130 ?140 120 40 50 60 70 80 90 100 110 30 20 1 10 100 1000 06023-013 thd, harmonics (db) sfdr (db) frequency (khz) second harmonic third harmonic thd sfdr figure 14. thd, harmonics, and sfdr vs. frequency 0 ?140 ?120 ?100 ?80 ?60 ?40 ?20 ?160 ?180 0 100 200 300 400 500 600 700 800 900 1000 06023-014 amplitude (db of full scale) frequency (khz) f s = 2msps f in =100.7khz snr = 91db thd = ?100db sfdr = 101db sinad = 90.5db figure 15. fft 100 khz 06023-015 snr, sinad (db) enob (bits) temperature (c) ?55 ?35 ?15 5 25 45 65 85 105 125 14.0 14.5 15.0 15.5 16.0 86 87 90 89 88 91 92 93 94 snr enob sinad figure 16. snr, sinad, and enob vs. temperature 06023-016 thd, harmonics (db) sfdr (db) temperature (c) ?55 ?35 ?15 5 25 45 65 85 105 125 sfdr thd second harmonic third harmonic 60 70 80 90 100 110 120 ?140 ?130 ?120 ?110 ?100 ?90 ? 80 figure 17. thd, harmonics, and sfdr vs. temperature
ad7622 rev. 0 | page 14 of 28 93.0 92.0 91.5 92.5 91.0 ?60 ?50 ?40 ?30 ?20 ?10 0 06023-017 snr, sinad referred to full scale (db) input level (db) snr sinad figure 18. snr and sinad vs. input level (referred to full scale) 16 0 ?55 125 temperature (c) operating currents (a) 14 12 10 8 6 4 2 ?35?155 25456585105 dvdd ovdd, 3.3v ovdd, 2.5v avdd 06023-018 figure 19. power-down operating currents vs. temperature 100k 0.01 10 10m sampling rate (sps) operating currents (a) 100 1k 10k 100k 1m 0.1 1 10 100 1k 10k avdd dvdd ovdd = 3.3v, all modes ovdd = 2.5v, all modes pdref = pdbuf = high 06023-019 figure 20. operating currents vs. sample rate 20 4 4 c l (pf) t 12 delay (ns) 18 16 14 12 10 8 6 50 100 150 200 ovdd = 2.5v @ 85c ovdd = 3.3v @ 85c ovdd = 3.3v @ 25c ovdd = 2.5v @ 25c 06023-020 figure 21. typical delay vs. load capacitance c l
ad7622 rev. 0 | page 15 of 28 applications information 0 6023-021 sw+ comp sw? in+ ref refgnd lsb msb 32,768c 16,384c 4c 2c c c switches control control logic busy output code cnvst in? 32,768c 16,384c 4c 2c c c lsb msb agnd agnd figure 22. adc simplified schematic circuit information the ad7622 is a very fast, low power, single-supply, precise 16-bit adc using successive approximation architecture. the ad7622 features different modes to optimize performances according to the applications. in warp mode, the ad7622 is capable of converting 2,000,000 samples per second (2 msps). the ad7622 provides the user with an on-chip track-and-hold, successive approximation adc that does not exhibit any pipeline or latency, making it ideal for multiple multiplexed channel applications. the ad7622 can operate from a single 2.5 v supply and interface to either 5 v, 3.3 v, or 2.5 v digital logic. it is housed in a 48-lead lqfp package or a tiny 48-lead lfcsp package, which combines space savings with flexibility and allows the ad7622 to be configured as either a serial or a parallel interface. the ad7622 is pin-to-pin compatible with other pulsar adcs and is a speed upgrade of the ad7677 . converter operation the ad7622 is a successive approximation adc based on a charge redistribution dac. figure 22 shows the simplified schematic of the adc. the capacitive dac consists of two identical arrays of 16 binary weighted capacitors that are connected to the two comparator inputs. during the acquisition phase, terminals of the array tied to the comparators input are connected to agnd via sw+ and sw?. all independent switches are connected to the analog inputs. therefore, the capacitor arrays are used as sampling capacitors and acquire the analog signal on the in+ and in? inputs. a conversion phase is initiated once the acquisition phase is complete and the cnvst input goes low. when the conversion phase begins, sw+ and sw? are opened first. the two capacitor arrays are then disconnected from the inputs and connected to the refgnd input. therefore, the differential voltage between the inputs (in+ and in?) captured at the end of the acquisition phase is applied to the comparator inputs, causing the comparator to become unbalanced. by switching each element of the capacitor array between refgnd and ref, the comparator input varies by binary weighted voltage steps (v ref /2, v ref /4 throughv ref /65536). the control logic toggles these switches, starting with the msb first, to bring the comparator back into a balanced condition. after the completion of this process, the control logic generates the adc output code and brings busy output low. modes of operation the ad7622 features three modes of operations: wideband warp, warp, and normal. each of these modes is more suitable for specific applications. the wideband warp (warp = high, normal = high) and warp (warp = high, normal = low) modes allow the fastest conversion rate of up to 2 msps. however, in these modes, the full specified accuracy is guaranteed only when the time between conversions does not exceed 1 ms. if the time between two consecutive conversions is longer than 1 ms (for instance after power-up), the first conversion result should be ignored. these modes make the ad7622 ideal for applications where both high accuracy and fast sample rates are required. wideband warp mode offers slightly improved linearity and thd over warp mode. normal mode ( normal = low, warp = low) is the fastest mode (1.5 msps) without any limitation on time between conversions. this mode makes the ad7622 ideal for asynchronous applications, such as data acquisition systems, where both high accuracy and fast sample rates are required.
ad7622 rev. 0 | page 16 of 28 transfer functions using the ob/ 2c digital input, the ad7622 offers two output codings: straight binary and twos complement. the lsb size with v ref = 2.048 v is 2 v ref / 65536 which is 62.5 v. refer to figure 23 and table 7 for the ideal transfer characteristic. 000...000 000...001 000...010 111...101 111...110 111...111 adc code (straight binary) analog input +fsr ? 1.5 lsb +fsr ? 1 lsb ?fsr + 1 lsb ?fsr ?fsr + 0.5 lsb 06023-022 figure 23. adc ideal transfer function table 7. output codes and ideal input voltages digital output code (hex) description analog input v ref = 2.048 v straight binary twos complement fsr ?1 lsb +2.047938 v 0xffff 1 0x7fff 1 fsr ? 2 lsb +2.047875 v 0xfffe 0x7ffe midscale + 1 lsb +62.5 v 0x8001 0x0001 midscale 0 v 0x8000 0x0000 midscale ? 1 lsb ?62.5 v 0x7fff 0xffff ?fsr + 1 lsb ?2.047938 v 0x0001 0x8001 ?fsr ?2.048 v 0x0000 2 0x8000 2 1 this is also the code fo r overrange analog input (v in+ ? v in? above +v ref ? v refgnd ). 2 this is also the code fo r underrange analog input (v in+ ? v in? below ?v ref + v refgnd ). 06023-023 rd cs 100nf 100nf avdd 10f 100nf agnd dgnd dvdd ovdd ognd cnvst busy sdout sclk reset pd refbufin 10? d clock ad7622 microconverter/ microprocessor/ dsp serial port digital interface supply (2.5v or 3.3v) analog supply (2.5v) ovdd warp digital supply (2.5v) in+ in? u2 15 ? note 5 50? 50pf note 1 analog input + c c c c 2.7nf 2.7nf u1 15? note 1 ser/par ob/2c refgnd ref pdbuf pdref 100nf analog input ? note 2 note 2 note 3 note 4 note 3 note 7 note 6 normal 10f 10f c ref 10f 10k ? 50pf 1. see analog inputs section. 2. the ad8021 is recommended. see driver amplifier choice section. 3. the configuration shown is using the internal reference. see voltage reference input section. 4. a 10f ceramic capacitor (x5r, 1206 size) is recommended (for example, panasonic ecj3yb0j106m). see voltage reference input section. 5. option, see power supply section. 6. option, see power-up section. 7. optional low jitter cnvst, see conversion control section. figure 24. typical connection diagram
ad7622 rev. 0 | page 17 of 28 typical connection diagram figure 24 shows a typical connection diagram for the ad7622. different circuitry shown in this diagram is optional and is discussed in the following sections. analog inputs figure 25 shows an equivalent circuit of the input structure of the ad7622. the two diodes, d 1 and d 2 , provide esd protection for the analog inputs in+ and in?. care must be taken to ensure that the analog input signal never exceeds the supply rails by more than 0.3 v, because this causes the diodes to become forward- biased and to start conducting current. these diodes can handle a forward-biased current of 100 ma maximum. for instance, these conditions could eventually occur when the input buffers u1 or u2 supplies are different from avdd. in such a case, an input buffer with a short-circuit current limitation can be used to protect the part. d 1 r in c in d 2 in+ or in? agnd a v dd c pin 06023-024 figure 25. ad7622 simplified analog input the analog input of the ad7622 is a true differential structure. by using this differential input, small signals common to both inputs are rejected, as shown in figure 26 , representing the typical cmrr over frequency with internal and external references. 75 45 1 10000 frequency (khz) cmrr (db) 10 100 1000 50 55 60 65 70 06023-025 int ref ext ref figure 26. analog input cmrr vs. frequency during the acquisition phase for ac signals, the impedance of the analog inputs, in+ and in?, can be modeled as a parallel combination of capacitor c pin and the network formed by the series connection of r in and c in . c pin is primarily the pin capacitance. r in is typically 175 and is a lumped component comprised of some serial resistors and the on resistance of the switches. c in is typically 12 pf and is mainly the adc sampling capacitor. during the conversion phase, when the switches are opened, the input impedance is limited to c pin . r in and c in make a 1-pole, low-pass filter that has a typical ?3 db cutoff frequency of 50 mhz, thereby reducing an undesirable aliasing effect and limiting the noise coming from the inputs. because the input impedance of the ad7622 is very high, the ad7622 can be directly driven by a low impedance source without gain error. to further improve the noise filtering achieved by the ad7622s analog input circuit, an external 1-pole rc filter between the amplifiers outputs and the adc analog inputs can be used, as shown in figure 24 . however, large source impedances significantly affect the ac performance, especially the total harmonic distortion (thd). the maximum source impedance depends on the amount of thd that can be tolerated. the thd degrades as a function of the source impedance and the maximum input frequency, as shown in figure 27 . ? 60 ?105 1 1000 thd (db) 10 100 ?95 ?85 ?75 ?65 ?100 ?90 ?80 ?70 06023-026 input frequency (khz) r s = 500 ? r s = 100 ? r s = 50 ? r s = 15 ? figure 27. thd vs. analog input frequency and source resistance multiplexed inputs when using the full 2 msps throughput in multiplexed applications for a full-scale step, the rc filter, as shown in figure 24 , does not settle in the required acquisition time, t 8 . these values are chosen to optimize the best snr performance of the ad7622. to use the full 2 msps throughput in multiplexed applications, the rc should be adjusted to satisfy t 8 (which is ~ 7 rc time constant). however, lowering r and c increases the rc filter bandwidth and allows more noise into the ad7622, which degrades snr. to preserve the snr performance in these applications using the rc filter shown in figure 24 , the ad7622 should be run with t 8 > 280 ns; or approximately 1/(t 7 + t 8 ) ~ 1.55 msps in wideband and warp modes.
ad7622 rev. 0 | page 18 of 28 driver amplifier choice although the ad7622 is easy to drive, the driver amplifier needs to meet the following requirements: ? for multichannel, multiplexed applications, the driver amplifier and the ad7622 analog input circuit must be able to settle for a full-scale step of the capacitor array at an 16-bit level (0.0015%). in the amplifiers data sheet, settling at 0.1% to 0.01% is more commonly specified. this could differ significantly from the settling time at a 16-bit level and should be verified prior to driver selection. the ad8021 op amp, which combines ultralow noise and high gain bandwidth, meets this settling time requirement even when used with gains up to 13. ? the noise generated by the driver amplifier needs to be kept as low as possible to preserve the snr and transition noise performance of the ad7622. the noise coming from the driver is filtered by the ad7622 analog input circuit 1-pole, low-pass filter made by r in and c in or by the external filter, if one is used. the snr degradation due to the amplifier is () () ? ? ? ? ? ? ? ? ? ? ? ? ? ? + + = ? ? + ? 2 2 2 2 2 45 45 20log n 3db n 3db loss ne f ne f snr where: f C3db is the input bandwidth of the ad7622 (50 mhz) or the cutoff frequency of the input rc filter shown in figure 24 (3.9 mhz), if one is used. n is the noise factor of the amplifier (1 in buffer configuration). e n+ and e n? are the equivalent input voltage noise densities of the op amps connected to in+ and in?, in nv/hz. this approximation can be used when the resistances used around the amplifier are small. if larger resistances are used, their noise contributions should also be root-sum squared. for instance, when using op amps with an equivalent input noise density of 2.1 nv/hz, such as the ad8021 , with a noise gain of 1 when configured as a buffer, degrades the snr by only 0.1 db when using the rc filter in figure 24 , and by 1.3 db without it. ? the driver needs to have a thd performance suitable to that of the ad7622. figure 14 gives the thd vs. frequency that the driver should exceed. the ad8021 meets these requirements and is appropriate for almost all applications. the ad8021 needs a 10 pf external compensation capacitor that should have good linearity as an npo ceramic or mica type. moreover, the use of a noninverting 1 gain arrangement is recommended and helps to obtain the best signal-to-noise ratio. the ad8022 can also be used when a dual version is needed and a gain of 1 is present. the ad829 is an alternative in applications where high frequency (above 100 khz) performance is not required. in applications with a gain of 1, an 82 pf compensation capacitor is required. the ad8610 is an option when low bias current is needed in low frequency applications. refer to table 8 for some recommended op amps. table 8. recommended driver amplifiers amplifier typical application ada4841-x very low noise, low distortion, low power, low frequency ad829 very low noise, low frequency ad8021 very low noise, high frequency ad8022 very low noise, high frequency, dual ad8610 / ad8620 low bias current, low frequency, single/dual single-to-differential driver for applications using unipolar analog signals, a single-ended- to-differential driver, as shown in figure 28 , allows for a differential input into the part. this configuration, when provided an input signal of 0 to v ref , produces a differential v ref with midscale at v ref /2. the 1-pole filter using r = 15 and c = 2.7nf provides a corner frequency of 3.9 mhz. if the application can tolerate more noise, the ad8139 differential driver can be used. ad8021 analog input ( unipolar 0 v to 2.048v) ad8021 in+ in? ad7622 ref 10 f 15 ? 15 ? 100nf 2.7nf 2.7nf u2 u1 10pf 10pf 5k ? 5k ? 590 ? 590 ? 06023-041 figure 28. single-ended-to- differential driver circuit (internal reference buffer used)
ad7622 rev. 0 | page 19 of 28 voltage reference input the ad7622 allows the choice of either a very low temperature drift internal voltage reference, an external 1.2 v reference that can be buffered using the internal reference buffer, or an external reference. unlike many adcs with internal references, the internal reference of the ad7622 provides excellent performance and can be used in almost all applications. internal reference (pdbuf = low, pdref = low) to use the internal reference, the pdref and pdbuf inputs must both be low. this produces a 1.2 v band gap output on refbufin, which is amplified by the internal buffer and results in a 2.048 v reference on the ref pin. the internal reference is temperature compensated to 2.048 v 10 mv. the reference is trimmed to provide a typical drift of 8 ppm/c. this typical drift characteristic is shown in figure 8 . the output resistance of refbufin is 6.33 k (minimum) when the internal reference is enabled. it is necessary to decouple this with a ceramic capacitor greater than 100 nf. therefore, the capacitor provides an rc filter for noise reduction. because the output impedance of refbufin is typically 6.33 k, relative humidity (among other industrial contaminates) can directly affect the drift characteristics of the reference. typically, a guard ring is used to reduce the effects of drift under such circumstances. however, because the ad7622 has a fine lead pitch, guarding this node is not practical. therefore, in these industrial and other types of applications, it is recommended to use a conformal coating, such as dow corning? 1-2577 or humiseal? 1b73. external 1.2 v reference and internal buffer (pdbuf = low, pdref = high) to use an external reference along with the internal buffer, pdref should be high and pdbuf should be low. this powers down the internal reference and allows an external 1.2 v reference to be applied to refbufin, producing 2.048 v (typically) on the ref pin. external 2.5 v reference (pdbuf = high, pdref = high) to use an external 2.5 v reference directly on the ref pin, pdref and pdbuf should both be high. for improved drift performance, an external reference, such as the ad780 , adr421 , adr431 , or adr441 , can be used. the advantages of directly using the external voltage reference are: ? the snr and dynamic range improvement (about 1.7 db) resulting from the use of a reference voltage very close to the supply (2.5 v) instead of a typical 2.048 v reference when the internal reference is used. this is calculated by ? ? ? ? ? ? = 50.2 048.2 log20 snr ? the power savings when the internal reference is powered down (pdref high). pdref and pdbuf power down the internal reference and the internal reference buffer, respectively. the input current of pdref and pdbuf should never exceed 20 ma. this can occur when the driving voltage is above avdd (for instance, at power-up). in this case, a 125 series resistor is recommended. reference decoupling whether using an internal or external reference, the ad7622 voltage reference input (ref) has a dynamic input impedance; therefore, it should be driven by a low impedance source with efficient decoupling between the ref and refgnd inputs. this decoupling depends on the choice of the voltage reference but usually consists of a low esr capacitor connected to ref and refgnd with minimum parasitic inductance. a 10 f (x5r, 1206 size) ceramic chip capacitor (or 47 f tantalum capacitor) is appropriate when using either the internal reference or one of the recommended reference voltages. the placement of the reference decoupling is also important to the performance of the ad7622. the decoupling capacitor should be mounted on the same side as the adc right at the ref pin with a thick pcb trace. the refgnd should also connect to the reference decoupling capacitor with the shortest distance. for applications that use multiple ad7622 devices, it is more effective to use an external reference with the internal reference buffer to buffer the reference voltage. however, because the reference buffers are not unity gain, ratiometric, simultaneously sampled designs should use an external reference and external buffer, such as the ad8031 / ad8032 ; therefore, preserving the same reference level for all converters. the voltage reference temperature coefficient (tc) directly impacts full scale; therefore, in applications where full-scale accuracy matters, care must be taken with the tc. for instance, a 15 ppm/c tc of the reference changes full scale by 1 lsb/c. note that v ref can be increased to avdd + 0.1 v. because the input range is defined in terms of v ref , this would essentially increase the range to 0 v to 2.8 v with an avdd = 2.7 v.
ad7622 rev. 0 | page 20 of 28 temperature sensor the temp pin measures the temperature of the ad7622. to improve the calibration accuracy over the temperature range, the output of the temp pin is applied to one of the inputs of the analog switch (such as, adg779 ), and the adc itself is used to measure its own temperature. this configuration is shown in figure 29 . adg779 ad8021 c c analog input (unipolar) ad7622 in+ temperature sensor temp 06023-027 figure 29. use of the temperature sensor power supply the ad7622 uses three sets of power supply pins: an analog 2.5 v supply avdd, a digital 2.5 v core supply dvdd, and a digital input/output interface supply ovdd. the ovdd supply allows direct interface with any logic working between 2.3 v and 5.25 v. to reduce the number of supplies needed, the digital core (dvdd) can be supplied through a simple rc filter from the analog supply, as shown in figure 24 . power sequencing the ad7622 is independent of power supply sequencing and thus free from supply induced voltage latch-up. in addition, it is very insensitive to power supply variations over a wide frequency range, as shown in figure 30 . 65.0 45.0 1 10000 frequency (khz) psrr (db) 10 100 1000 47.5 50.0 52.5 55.0 57.5 60.0 62.5 06023-029 ext ref int ref figure 30. psrr vs. frequency power-up at power-up, or when returning to operational mode from the power-down mode (pd = high), the ad7622 engages an initialization process. during this time, the first 128 conversions should be ignored or the reset input could be pulsed to engage a faster initialization process. refer to the digital interface section for reset and timing details. a simple power-on reset circuit, as shown in figure 24 , can be used to minimize the digital interface. as ovdd powers up, the capacitor is shorted and brings reset high; it is then charged returning reset to low. however, this circuit only works when powering up the ad7622 because the power-down mode (pd = high) does not power down any of the supplies and as a result, reset is low. it should be noted that the digital interface remains active even during the acquisition phase. to reduce the operating digital supply currents even further, drive the digital inputs close to the power rails (that is, ovdd and ognd). conversion control the ad7622 is controlled by the cnvst input. a falling edge on cnvst is all that is necessary to initiate a conversion. detailed timing diagrams of the conversion process are shown in figure 31 . once initiated, it cannot be restarted or aborted, even by the power-down input, pd, until the conversion is complete. the cnvst signal operates independently of cs and rd signals. busy mode convert acquire acquire convert cnvst t 1 t 2 t 4 t 3 t 5 t 6 t 7 t 8 06023-030 figure 31. basic conversion timing for optimal performance, the rising edge of cnvst should not occur after the maximum cnvst low time, t 1 , or until the end of conversion. although cnvst is a digital signal, it should be designed with special care with fast, clean edges and levels with minimum overshoot and undershoot or ringing. the cnvst trace should be shielded with ground and a low value serial resistor (for example, 50 ) termination should be added close to the output of the component that drives this line. in addition, a 50 pf capacitor is recommended to further reduce the effects of overshoot and undershoot as shown in figure 24 . for applications where snr is critical, the cnvst signal should have very low jitter. this can be achieved by using a dedicated oscillator for cnvst generation, or by clocking cnvst with a high frequency, low jitter clock, as shown in figure 24 .
ad7622 rev. 0 | page 21 of 28 interfaces digital interface the ad7622 has a versatile digital interface that can be set up as either a serial or a parallel interface with the host system. the serial interface is multiplexed on the parallel data bus. the ad7622 digital interface also accommodates 2.5 v, 3.3 v, or 5 v logic with either ovdd at 2.5 v or 3.3 v. ovdd defines the logic high output voltage. in most applications, the ovdd supply pin of the ad7622 is connected to the host system interface 2.5 v or 3.3 v digital supply. by using the ob/ 2c input pin, either twos complement or straight binary coding can be used. the two signals cs and rd control the interface. when at least one of these signals is high, the interface outputs are in high impedance. usually, cs allows the selection of each ad7622 in multicircuit applications and is held low in a single ad7622 design. rd is generally used to enable the conversion result on the data bus. reset the reset input is used to reset the ad7622 and generate a fast initialization. a rising edge on reset aborts the current conversion (if any) and tristates the data bus. the falling edge of reset clears the data bus and engages the initialization process indicated by pulsing busy high. conversions can take place after the falling edge of busy. refer to figure 32 for the reset timing details. reset data busy cnvst t 38 t 39 t 8 t 9 06023-031 figure 32. reset timing parallel interface the ad7622 is configured to use the parallel interface when ser/ par is held low. master parallel interface data can be continuously read by tying cs and rd low, thus requiring minimal microprocessor connections. however, in this mode, the data bus is always driven and cannot be used in shared bus applications, unless the device is held in reset. figure 33 details the timing for this mode. 04761-032 t 1 busy data bus previous conversion data new data cnvst cs = rd = 0 t 10 t 4 t 11 t 3 figure 33. master parallel data timing for reading (continuous read) slave parallel interface in slave parallel reading mode, the data can be read either after each conversion, which is during the next acquisition phase, or during the following conversion, as shown in figure 34 and figure 35 , respectively. when the data is read during the conversion, it is recommended that it is read-only during the first half of the conversion phase. this avoids any potential feedthrough between voltage transients on the digital interface and the most critical analog conversion circuitry. 04761-033 current conversion t 13 t 12 busy data bus rd cs figure 34. slave parallel data timing for reading (read after convert) previous conversion t 13 t 12 t 3 busy data bus cnvst, rd cs = 0 t 4 t 1 06023-042 figure 35. slave parallel data timing for reading (read during convert)
ad7622 rev. 0 | page 22 of 28 8-bit interface (master or slave) the byteswap pin allows a glueless interface to an 8-bit bus. as shown in figure 36 , when byteswap is low, the lsb byte is output on d[7:0] and the msb is output on d[15:8]. when byteswap is high, the lsb and msb bytes are swapped, and the lsb is output on d[15:8] and the msb is output on d[7:0]. by connecting byteswap to an address line, the 16-bit data can be read in two bytes on either d[15:8] or d[7:0]. this interface can be used in both master and slave parallel reading modes. cs rd byteswap pins d[15:8] pins d[7:0] hi-z hi-z high byte low byte low byte high byte hi-z hi-z t 12 t 12 t 13 06023-034 figure 36. 8-bit and 16-bit parallel interface serial interface the ad7622 is configured to use the serial interface when ser/ par = high. the ad7622 outputs 16 bits of data, msb first, on the sdout pin. this data is synchronized with the 16 clock pulses provided on the sclk pin. the output data is valid on both the rising and falling edge of the data clock. master serial interface internal clock the ad7622 is configured to generate and provide the serial data clock sclk when the ext/ int pin = low. the ad7622 also generates a sync signal to indicate to the host when the serial data is valid. the serial clock sclk and the sync signal can be inverted. depending on the state of the read during convert input, rdc/sdin, the data can be read after each conversion or during the following conversion. figure 37 and figure 38 show detailed timing diagrams of these two modes. usually, because the ad7622 is used with a fast throughput, the master read during conversion mode, rdc/sdin = high, is the most recommended serial mode. in this mode, the serial clock and data toggle at appropriate instants, minimizing potential feedthrough between digital activity and critical conversion decisions. in this mode, the sclk period changes because the lsbs require more time to settle and the sclk is derived from the sar conversion cycle. in read after conversion mode, rdc/sdin = low, it should be noted that unlike other modes, the busy signal returns low after the 16 data bits are pulsed out and not at the end of the conversion phase, resulting in a longer busy width. as a result, the maximum throughput cannot be achieved in this mode. in addition, in read after co nvert mode, the sclk frequency can be slowed down to accommodate different hosts using the divsclk[1:0] inputs. refer to table 4 for the sclk timing details when using these inputs.
ad7622 rev. 0 | page 23 of 28 busy sync sclk s dout 1 2 3 14 15 16 d15 d14 d2 d1 d0 x rdc/sdin = 0 invsclk = invsync = 0 cnvst cs, rd ext/int = 0 t 23 t 22 t 16 t 15 t 14 t 29 t 19 t 21 t 20 t 18 t 28 t 30 t 24 t 25 t 26 t 27 t 3 06023-035 figure 37. master serial data timing for reading (read after convert) ext/int = 0 rdc/sdin = 1 invsclk = invsync = 0 d15 d14 d2 d1 d0 x 123 141516 busy sync sclk sdout cnvst cs, rd t 23 t 18 t 15 t 14 t 17 t 3 t 22 t 16 t 1 t 25 t 26 t 24 t 27 t 19 t 20 t 21 06023-036 figure 38. master serial data timing for reading (read previous conversion during convert)
ad7622 rev. 0 | page 24 of 28 slave serial interface external clock the ad7622 is configured to accept an externally supplied serial data clock on the sclk pin when the ext/ int pin is held high. in this mode, severa l methods can be used to read the data. the external serial clock is gated by cs . when cs and rd are both low, the data can be read after each conversion or during the following conversion. the external clock can be either a continuous or a discontinuous clock. a discontinuous clock can be either normally high or normally low when inactive. figure 40 and figure 41 show the detailed timing diagrams of these methods. while the ad7622 is performing a bit decision, it is important that voltage transients be avoided on digital input/output pins or degradation of the conversion result could occur. this is particularly important during the second half of the conversion phase because the ad7622 provides error correction circuitry that can correct for an improper bit decision made during the first half of the conversion phase. for this reason, it is recommended that when an external clock is being provided, a discontinuous clock is toggled only when busy is low or, more importantly, that it does not transition during the latter half of busy high. external discontinuous clock data read after conversion though the maximum throughput cannot be achieved using this mode, it is the most recommended of the serial slave modes. figure 40 shows the detailed timing diagrams of this method. after a conversion is complete, indicated by busy returning low, the conversion result can be read while both cs and rd are low. data is shifted out msb first with 16 clock pulses and is valid on the rising and falling edges of the clock. among the advantages of this method is the fact that conversion performance is not degraded because there are no voltage transients on the digital interface during the conversion process. another advantage is the ability to read the data at any speed up to 80 mhz, which accommodates both the slow digital host interface and the fast serial reading. it is also possible to begin to read data after conversion and continue to read the last bits after a new conversion is initiated. in this reading mode, it is recommended to pause digital activity just prior to initiating a conversion (sclk should be held high or low). once the co nversion has begun, the reading can continue. in addition, in this mode, the use of a slower clock speed can be used to read the data because the total reading time is the acquisition time, t 8 + half of the conversion time, t 7 (t 8 + ? t 7 , see the external clock data read during previous conversion section). finally, in this mode only, the ad7622 provides a daisy-chain feature using the rdc/sdin pin for cascading multiple converters together. this feature is useful for reducing component count and wiring connections when desired, as, for instance, in isolated multiconverter applications. an example of the concatenation of two devices is shown in figure 39 . simultaneous sampling is possible by using a common cnvst signal. it should be noted that the rdc/sdin input is latched on the edge of sclk opposite to the one used to shift out the data on sdout. therefore, the msb of the upstream converter just follows the lsb of the downstream converter on the next sclk cycle. sclk sdout rdc/sdin ad7622 #1 (downstream) ad7622 #2 (upstream) busy out busy busy data out sclk rdc/sdin sdout sclk in cnvst in cnvst cs cnvst cs cs in 06023-037 figure 39. two ad7622 devices in a daisy-chain configuration external clock data read during previous conversion figure 41 shows the detailed timing diagrams of this method. during a conversion, while cs and rd are both low, the result of the previous conversion can be read. the data is shifted out, msb first, with 16 clock pulses and is valid on both the rising and falling edge of the clock. the 16 bits have to be read before the current conversion is complete; otherwise, rderror is pulsed high and can be used to interrupt the host interface to prevent incomplete data reading. there is no daisy-chain feature in this mode, and the rdc/sdin input should always be tied either high or low. to reduce performance degradation due to digital activity, a fast discontinuous clock (at least 60 mhz when normal mode is used, or 80 mhz when warp mode is used) is recommended to ensure that all the bits are read during the first half of the sar conversion phase. if the maximum throughput is not used, thus allowing more acquisition time, then the use of a slower clock speed can be used to read the data.
ad7622 rev. 0 | page 25 of 28 sclk s dout d15 d14 d1 d0 d13 x15 x14 x13 x1 x0 y15 y14 busy sdin invsclk = 0 x15 x14 x 123 1415161718 ext/int = 1 cs rd = 0 t 33 t 16 t 34 t 31 t 32 t 35 t 36 t 37 06023-038 figure 40. slave serial data timing for reading (read after convert) s dout sclk d1 d0 x d15 d14 d13 12 3 141516 busy ext/int = 1 invsclk = 0 cnvst cs rd = 0 t 16 t 31 t 32 t 35 t 3 t 36 t 37 06023-039 figure 41. slave serial data timing for reading (read previous conversion during convert)
ad7622 rev. 0 | page 26 of 28 microprocessor interfacing the ad7622 is ideally suited for traditional dc measurement applications supporting a microprocessor, and ac signal processing applications interfacing to a digital signal processor. the ad7622 is designed to interface with a parallel 8-bit or 16-bit wide interface or with a general-purpose serial port or i/o ports on a microcontroller. a variety of external buffers can be used with the ad7622 to prevent digital noise from coupling into the adc. the spi interface (adsp-219x) section illustrates the use of the ad7622 with the adsp-219x spi-equipped dsp. spi interface (adsp-219x) figure 42 shows an interface diagram between the ad7622 and an spi-equipped dsp, the adsp-219x. to accommodate the slower speed of the dsp, the ad7622 acts as a slave device and data must be read after conversion. this mode also allows the daisy-chain feature. the convert command can be initiated in response to an internal timer interrupt. the 16-bit output data are read with three spi byte access. the reading process can be initiated in response to the end-of-conversion signal (busy going low) using an interrupt line of the dsp. the serial peripheral interface (spi) on the adsp-219x is configured for master mode (mstr) = 1, clock polarity bit (cpol) = 0, clock phase bit (cpha) = 1, and the spi interrupt enable (timod) = 00 by writing to the spi control register (spicltx). it should be noted that to meet all timing requirements, the spi clock should be limited to 17 mbps, allowing it to read an adc result in less than 1 s. when a higher sampling rate is desired, it is recommended to use one of the parallel interface modes. busy cs sdout sclk cnvst ad7622 pfx spixsel (pfx) misox sckx pfx or tfsx adsp-219x 1 dvdd mode0 mode1 ext/int rd invsclk 1 additional pins omitted for clarity. 06023-040 figure 42. interfacing the ad7622 to adsp-219x
ad7622 rev. 0 | page 27 of 28 application hints layout while the ad7622 has very good immunity to noise on the power supplies, exercise care with the grounding layout. to facilitate the use of ground planes that can be easily separated, design the printed circuit board that houses the ad7622 so that the analog and digital sections are separated and confined to certain areas of the board. digital and analog ground planes should be joined in only one place, preferably underneath the ad7622, or as close as possible to the ad7622. if the ad7622 is in a system where multiple devices require analog-to-digital ground connections, the connections should still be made at one point only, a star ground point, established as close as possible to the ad7622. to prevent coupling noise onto the die, avoid radiating noise, and reduce feedthrough: ? do not run digital lines under the device. ? run the analog ground plane under the ad7622. ? shield fast switching signals, like cnvst or clocks, with digital ground to avoid radiating noise to other sections of the board, and never run them near analog signal paths. ? avoid crossover of digital and analog signals. ? run traces on different but close layers of the board, at right angles to each other, to reduce the effect of feedthrough through the board. the power supply lines to the ad7622 should use as large a trace as possible to provide low impedance paths and reduce the effect of glitches on the power supply lines. good decoupling is also important to lower the impedance of the supplies presented to the ad7622, and to reduce the magnitude of the supply spikes. decoupling ceramic capacitors, typically 100 nf, should be placed on each of the power supplies pins, avdd, dvdd, and ovdd. the capacitors should be placed close to, and ideally right up against, these pins and their corresponding ground pins. additionally, low esr 10 f capacitors should be located in the vicinity of the adc to further reduce low frequency ripple. the dvdd supply of the ad7622 can be either a separate supply or come from the analog supply, avdd, or from the digital interface supply, ovdd. when the system digital supply is noisy, or fast switching digital signals are present, and no separate supply is available, it is recommended to connect the dvdd digital supply to the analog supply avdd through an rc filter, and to connect the system supply to the interface digital supply ovdd and the remaining digital circuitry. refer to figure 24 for an example of this configuration. when dvdd is powered from the system supply, it is useful to insert a bead to further reduce high frequency spikes. the ad7622 has four different ground pins: refgnd, agnd, dgnd, and ognd. refgnd senses the reference voltage and, because it carries pulsed currents, should have a low impedance return to the reference. agnd is the ground to which most internal adc analog signals are referenced; it must be connected with the least resistance to the analog ground plane. dgnd must be tied to the analog or digital ground plane depending on the configuration. ognd is connected to the digital system ground. the layout of the decoupling of the reference voltage is important. to minimize parasitic inductances, place the decoupling capacitor close to the adc and connect it with short, thick traces. evaluating the ad7622 performance a recommended layout for the ad7622 is outlined in the documentation of the eval-ad7622-cb evaluation board for the ad7622. the evaluation board package includes a fully assembled and tested evaluation board, documentation, and software for controlling the board from a pc via the eval- control brd3 .
ad7622 rev. 0 | page 28 of 28 outline dimensions compliant to jedec standards mo-220-vkkd-2 pin 1 indicator top view 6.75 bsc sq 7.00 bsc sq 1 48 12 13 37 36 24 25 5.25 5.10 sq 4.95 0.50 0.40 0.30 0.30 0.23 0.18 0.50 bsc 12 max 0.20 ref 0.80 max 0.65 typ 1.00 0.85 0.80 5.50 ref 0.05 max 0.02 nom 0.60 max 0.60 max pin 1 indicator coplanarity 0.08 seating plane 0.25 min exposed p a d (bottom view) paddle connected to agnd. this connection is not required to meet the electrical performances. figure 43. 48-lead lead frame chip scale package [lfcsp_vq] 7 mm 7 mm body, very thin quad (cp-48-1) dimensions shown in millimeters compliant to jedec standards ms-026-bbc top view (pins down) 1 12 13 25 24 36 37 48 0.27 0.22 0.17 0.50 bsc lead pitch 7.00 bsc sq 1.60 max 0.75 0.60 0.45 view a 9.00 bsc sq pin 1 0.20 0.09 1.45 1.40 1.35 0.08 max coplanarity view a rotated 90 ccw seating plane 7 3.5 0 0.15 0.05 figure 44. 48-lead low profile quad flat package [lqfp] (st-48) dimensions shown in millimeters ordering guide model temperature range package description package option ad7622bcpz 1 ?40c to +85c 48-lead lead frame chip scale package (lfcsp_vq) cp-48-1 ad7622bcpzrl 1 ?40c to +85c 48-lead lead frame chip scale package (lfcsp_vq) cp-48-1 ad7622bstz 1 ?40c to +85c 48-lead low profile quad flat package (lqfp) st-48 ad7622bstzrl 1 ?40c to +85c 48-lead low profile quad flat package (lqfp) st-48 eval-ad7622cb 2 evaluation board eval-control brd3 3 controller board t 1 z = pb-free part. 2 this board can be used as a standalone evaluation board or in conjunction with the eval-control brd3 for evaluation/demonstrat ion purposes. 3 this board allows a pc to control and communicate with all analog devices, inc. evaluation boards ending in the cb designators . ?2006 analog devices, inc. all rights reserved. trademarks and registered trademarks are the property of their respective owners. d06023C0C 6/06(0) ttt

▲Up To Search▲

Price & Availability of AD7621

	To Download AD7621 Datasheet File
If you can't view the Datasheet, Please click here to try to view without PDF Reader .